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TS4871
OUTPUT RAIL TO RAIL 1W AUDIO POWER AMPLIFIER WITH STANDBY MODE
s OPERATING FROM VCC = 2.5V to 5.5V s 1W RAIL TO RAIL OUTPUT POWER @
Vcc=5V, THD=1%, f=1kHz, with 8 Load
TS4871IST - MiniSO8
1 2 3 4 8 7 6 5
PIN CONNECTIONS (Top View)
s ULTRA LOW CONSUMPTION IN STANDBY
MODE (10nA)
Standby Bypass VIN+ VINVOUT2 GND VCC VOUT1
s 75dB PSRR @ 217Hz from 5V to 2.6V s ULTRA LOW POP & CLICK s ULTRA LOW DISTORTION (0.1%) s UNITY GAIN STABLE s AVAILABLE IN SO8, MiniSO8 & DFN8 3x3mm
DESCRIPTION
TS4871ID-TS4871IDT - SO8
Standby
1 2 3 4
8 7 6 5
VOUT2 GND VCC VOUT1
The TS4871 is an Audio Power Amplifier capable of delivering 1W of continuous RMS Ouput Power into 8 load @ 5V. This Audio Amplifier is exhibiting 0.1% distortion level (THD) from a 5V supply for a Pout = 250mW RMS. An external standby mode control reduces the supply current to less than 10nA. An internal thermal shutdown protection is also provided. The TS4871 has been designed for high quality audio applications such as mobile phones and to minimize the number of external components. The unity-gain stable amplifier can be configured by external gain setting resistors. APPLICATIONS
Bypass VIN+ VIN-
TS4871IQT - DFN8
STANDBY BYPASS VIN+ VIN-
1 2 3 4
8 7 6 5
VOUT 2 GND Vcc VOUT 1
s Mobile Phones (Cellular / Cordless) s Laptop / Notebook Computers s PDAs s Portable Audio Devices
ORDER CODE
Part Number TS4871 Temperature Range: I -40, +85C Package Marking D * * * S Q 4871I 4871
Vcc Audio Input
TYPICAL APPLICATION SCHEMATIC
Cfeed Rfeed Vcc 6 Vcc Cs
Rin Cin
4 3
VinVin+
+
Vout1 5
RL 8 Ohms Av=-1 + Vout2 8
2 Rstb 1
Bypass Standby Bias GND
TS4871
Cb
7
MiniSO & DFN only available in Tape & Reel with T suffix(IST & IQT) D = Small Outline Package (SO) - also available in Tape & Reel (DT)
June 2003
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TS4871
ABSOLUTE MAXIMUM RATINGS
Symbol VCC Vi Toper Tstg Tj Rthja Supply voltage Input Voltage
2) 1)
Parameter
Value 6 GND to VCC -40 to + 85 -65 to +150 150 175 215 70 Internally Limited4) 2 200 Class A 260
Unit V V C C C C/W
Operating Free Air Temperature Range Storage Temperature Maximum Junction Temperature Thermal Resistance Junction to Ambient 3) SO8 MiniSO8 QNF8 Power Dissipation
Pd
ESD Human Body Model ESD Machine Model Latch-up Latch-up Immunity Lead Temperature (soldering, 10sec)
1. 2. 3. 4. All voltages values are measured with respect to the ground pin. The magnitude of input signal must never exceed VCC + 0.3V / G ND - 0.3V Device is protected in case of over temperature by a thermal shutdown active @ 150C. Exceeding the power derating curves during a long period, involves abnormal operating condition.
kV V C
OPERATING CONDITIONS
Symbol VCC VICM VSTB RL Rthja Supply Voltage Common Mode Input Voltage Range Standby Voltage Input : Device ON Device OFF Load Resistor Thermal Resistance Junction to Ambient SO8 MiniSO8 DFN8 2)
1)
Parameter
Value 2.5 to 5.5 GND to VCC - 1.2V GND VSTB 0.5V VCC - 0.5V VSTB VCC 4 - 32 150 190 41
Unit V V V C/W
1. This thermal resistance can be reduced with a suitable PCB layout (see Power Derating Curves Fig. 20)
2. When mounted on a 4 layers PCB
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TS4871
ELECTRICAL CHARACTERISTICS VCC = +5V, GND = 0V, Tamb = 25C (unless otherwise specified)
Symbol ICC ISTANDBY Voo Po THD + N PSRR M GM GBP Parameter Supply Current No input signal, no load Standby Current 1) No input signal, Vstdby = Vcc, RL = 8 Output Offset Voltage No input signal, RL = 8 Output Power THD = 1% Max, f = 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 250mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 Power Supply Rejection Ratio2) f = 217Hz, RL = 8, RFeed = 22K, Vripple = 200mV rms Phase Margin at Unity Gain RL = 8, CL = 500pF Gain Margin RL = 8, CL = 500pF Gain Bandwidth Product RL = 8 Min. Typ. 6 10 5 1 0.15 75 70 20 2 Max. 8 1000 20 Unit mA nA mV W % dB Degrees dB MHz
1. Standby mode is actived when Vstdby is tied to Vcc 2. Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is the surimposed sinus signal to Vcc @ f = 217Hz
VCC = +3.3V, GND = 0V, Tamb = 25C (unless otherwise specified)3)
Symbol ICC ISTANDBY Voo Po THD + N PSRR M GM GBP Parameter Supply Current No input signal, no load Standby Current 1) No input signal, Vstdby = Vcc, RL = 8 Output Offset Voltage No input signal, RL = 8 Output Power THD = 1% Max, f = 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 250mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 Power Supply Rejection Ratio2) f = 217Hz, RL = 8, RFeed = 22K, Vripple = 200mV rms Phase Margin at Unity Gain RL = 8, CL = 500pF Gain Margin RL = 8, CL = 500pF Gain Bandwidth Product RL = 8 Min. Typ. 5.5 10 5 450 0.15 75 70 20 2 Max. 8 1000 20 Unit mA nA mV mW % dB Degrees dB MHz
1. Standby mode is actived when Vstdby is tied to Vcc 2. Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is the surimposed sinus signal to Vcc @ f = 217Hz 3. All electrical values are made by correlation between 2.6V and 5V measurements
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TS4871
ELECTRICAL CHARACTERISTICS VCC = 2.6V, GND = 0V, Tamb = 25C (unless otherwise specified)
Symbol ICC ISTANDBY Voo Po THD + N PSRR M GM GBP Parameter Supply Current No input signal, no load Standby Current 1) No input signal, Vstdby = Vcc, RL = 8 Output Offset Voltage No input signal, RL = 8 Output Power THD = 1% Max, f = 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 200mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 Power Supply Rejection Ratio2) f = 217Hz, RL = 8, RFeed = 22K, Vripple = 200mV rms Phase Margin at Unity Gain RL = 8, CL = 500pF Gain Margin RL = 8, CL = 500pF Gain Bandwidth Product RL = 8 Min. Typ. 5.5 10 5 260 0.15 75 70 20 2 Max. 8 1000 20 Unit mA nA mV mW % dB Degrees dB MHz
1. Standby mode is actived when Vstdby is tied to Vcc 2. Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is the surimposed sinus signal to Vcc @ f = 217Hz
Components Rin Cin Rfeed Cs Cb Cfeed Rstb Gv
Functional Description Inverting input resistor which sets the closed loop gain in conjunction with Rfeed. This resistor also forms a high pass filter with Cin (fc = 1 / (2 x Pi x Rin x Cin)) Input coupling capacitor which blocks the DC voltage at the amplifier input terminal Feed back resistor which sets the closed loop gain in conjunction with Rin Supply Bypass capacitor which provides power supply filtering Bypass pin capacitor which provides half supply filtering Low pass filter capacitor allowing to cut the high frequency (low pass filter cut-off frequency 1 / (2 x Pi x Rfeed x Cfeed)) Pull-up resistor which fixes the right supply level on the standby pin Closed loop gain in BTL configuration = 2 x (Rfeed / Rin)
REMARKS 1. All measurements, except PSRR measurements, are made with a supply bypass capacitor Cs = 100F. 2. External resistors are not needed for having better stability when supply @ Vcc down to 3V. By the way, the quiescent current remains the same. 3. The standby response time is about 1s.
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TS4871
Fig. 1 : Open Loop Frequency Response Fig. 2 : Open Loop Frequency Response
0 60 Gain Vcc = 5V RL = 8 Tamb = 25C -20 -40 -60
Phase (Deg)
0 60 Gain Vcc = 5V ZL = 8 + 560pF Tamb = 25C -20 -40 -60
Phase (Deg)
40
Gain (dB)
40 Phase
Gain (dB)
Phase 20
-80 -100 -120
-80 -100 -120
20
0
-140 -160
0
-140 -160
-20
-180 -200
-20
-180 -200
-40 0.3
1
10
100
Frequency (kHz)
1000
10000
-220
-40 0.3
1
10
100 1000 Frequency (kHz)
10000
-220
Fig. 3 : Open Loop Frequency Response
Fig. 4 : Open Loop Frequency Response
80 60 40 Gain Vcc = 3.3V RL = 8 Tamb = 25C
0 -20 -40 -60 -80
80 60 40 Phase 20 0 -20 -40 0.3 Gain Vcc = 3.3V ZL = 8 + 560pF Tamb = 25C
0 -20 -40 -60 -80 -100 -120 -140 -160 -180 -200 -220 1 10 100 1000 Frequency (kHz) 10000 -240
Phase (Deg)
Phase (Deg)
Phase 20 0
-100 -120 -140 -160 -180 -200 -220 -240
-20 -40 0.3
1
10
100 1000 Frequency (kHz)
10000
Fig. 5 : Open Loop Frequency Response
Phase (Deg)
Gain (dB)
Fig. 6 : Open Loop Frequency Response
Gain (dB)
80 60 40
Gain (dB)
0 Gain Vcc = 2.6V RL = 8 Tamb = 25C -20 -40 -60 -80 Phase
Phase (Deg) Gain (dB)
80 Gain 60 40 Phase 20 0 -20 -40 0.3 Vcc = 2.6V ZL = 8 + 560pF Tamb = 25C
0 -20 -40 -60 -80 -100 -120 -140 -160 -180 -200 -220 1 10 100 1000 Frequency (kHz) 10000 -240
-100 -120 -140 -160 -180 -200 -220 -240
20 0 -20 -40 0.3
1
10
100 1000 Frequency (kHz)
10000
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TS4871
Fig. 7 : Open Loop Frequency Response Fig. 8 : Open Loop Frequency Response
100 80 60 Gain
Gain (dB)
-80 Phase -100 -120
Phase (Deg)
100 80 60 Gain
Gain (dB)
-80 Phase -100 -120 -140 -160
Phase (Deg)
40 20 0 -20 -40 0.3
-140 -160 -180 Vcc = 5V CL = 560pF Tamb = 25C 1 10 100 1000 Frequency (kHz) 10000 -200
40 20 -180 0 -20 Vcc = 3.3V CL = 560pF Tamb = 25C 1 10 100 1000 Frequency (kHz) 10000 -200 -220 -240
-220
-40 0.3
Fig. 9 : Open Loop Frequency Response
100 80 60 Gain
Gain (dB)
-80 Phase -100 -120 -140 -160
Phase (Deg)
40 20 -180 0 -20 -40 0.3 Vcc = 2.6V CL = 560pF Tamb = 25C 1 10 100 1000 Frequency (kHz) 10000 -200 -220 -240
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TS4871
Fig. 10 : Power Supply Rejection Ratio (PSRR) vs Power supply Fig. 11 : Power Supply Rejection Ratio (PSRR) vs Feedback Capacitor
-30 Vripple = 200mVrms Rfeed = 22 Input = floating RL = 8 Tamb = 25C
-10 -20 -30
PSRR (dB)
-40
PSRR (dB)
-50
-40 -50 -60
Vcc = 5, 3.3 & 2.6V Cb = 1F & 0.1F Rfeed = 22k Vripple = 200mVrms Input = floating RL = 8 Tamb = 25C
Cfeed=0 Cfeed=150pF Cfeed=330pF
-60
Vcc = 5V, 3.3V & 2.6V Cb = 1F & 0.1F
-70
-70
-80 10
Cfeed=680pF
100
1000 10000 Frequency (Hz)
100000
-80 10
100
1000 10000 Frequency (Hz)
100000
Fig. 12 : Power Supply Rejection Ratio (PSRR) vs Bypass Capacitor
Fig. 13 : Power Supply Rejection Ratio (PSRR) vs Input Capacitor
-10 -10 Cb=1F -20 Cb=10F -30
PSRR (dB)
Cin=1F Vcc = 5, 3.3 & 2.6V Rfeed = 22k Rin = 22k, Cin = 1F Rg = 100, RL = 8 Tamb = 25C Cb=47F Cin=330nF -20 Cin=220nF Vcc = 5, 3.3 & 2.6V Rfeed = 22k, Rin = 22k Cb = 1F Rg = 100, RL = 8 Tamb = 25C
-40 -50 -60 -70 -80 10 Cb=100F
PSRR (dB)
-30
-40 Cin=100nF -50 Cin=22nF
-60 10 100 1000
Frequency (Hz)
100
1000
Frequency (Hz)
10000
100000
10000
100000
Fig. 14 : Power Supply Rejection Ratio (PSRR) vs Feedback Resistor
-10 -20 -30
PSRR (dB)
-40 -50 -60
Vcc = 5, 3.3 & 2.6V Cb = 1F & 0.1F Vripple = 200mVrms Input = floating RL = 8 Tamb = 25C
Rfeed=110k Rfeed=47k
Rfeed=22k -70 Rfeed=10k -80 10 100 1000 10000 Frequency (Hz) 100000
7/28
TS4871
Fig. 15 : Pout @ THD + N = 1% vs Supply Voltage vs RL Fig. 16 : Pout @ THD + N = 10% vs Supply Voltage vs RL
1.4
Output power @ 1% THD + N (W)
2.0
Gv = 2 & 10 Cb = 1F F = 1kHz BW < 125kHz Tamb = 25C 8 6 4
Output power @ 10% THD + N (W)
1.2 1.0 0.8 0.6 0.4 0.2
1.8 1.6 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0.0 2.5
Gv = 2 & 10 Cb = 1F F = 1kHz BW < 125kHz Tamb = 25C
8 6 4
16
16
32 0.0 2.5 3.0 3.5
Vcc (V)
32 3.0 3.5
Vcc (V)
4.0
4.5
5.0
4.0
4.5
5.0
Fig. 17 : Power Dissipation vs Pout
Fig. 18 : Power Dissipation vs Pout
1.4 Vcc=5V 1.2 F=1kHz THD+N<1% 1.0 0.8 0.6 0.4 0.2 RL=16 0.0 0.0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 RL=8
0.6 Vcc=3.3V F=1kHz 0.5 THD+N<1%
Power Dissipation (W)
Power Dissipation (W)
RL=4
RL=4
0.4 0.3 0.2 RL=8 0.1 RL=16 0.0 0.0 0.2 0.4
Output Power (W)
0.6
0.8
Output Power (W)
Fig. 19 : Power Dissipation vs Pout
Fig. 20 : Power Derating Curves
0.40 0.35
Power Dissipation (W)
Vcc=2.6V F=1kHz THD+N<1%
Power Dissipation (W)
2.0 1.8
0.30 0.25 0.20 0.15 RL=8 0.10 0.05 0.00 0.0 RL=16 0.1 0.2
Output Power (W)
RL=4
1.6 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0.0 MiniSO8 0 25 50
QFN8
SO8
0.3
0.4
75
100
125
150
Ambiant Temperature (C)
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TS4871
Fig. 21 : THD + N vs Output Power
10 Rl = 4 Vcc = 5V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20kHz
Fig. 22 : THD + N vs Output Power
10 RL = 4, Vcc = 5V Gv = 10 Cb = Cin = 1F BW < 125kHz, Tamb = 25C
THD + N (%)
THD + N (%)
20kHz 1 20Hz
20Hz, 1kHz 0.1 1E-3 0.01 0.1 Output Power (W) 1
0.1 1E-3 0.01 0.1 Output Power (W)
1kHz 1
Fig. 23 : THD + N vs Output Power
10 RL = 4, Vcc = 3.3V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1
Fig. 24 : THD + N vs Output Power
10 RL = 4, Vcc = 3.3V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20kHz
THD + N (%)
20kHz
THD + N (%)
0.1 20Hz, 1kHz 0.1 1E-3 0.01 0.1 Output Power (W) 1 1E-3
20Hz 1kHz 0.01 0.1 Output Power (W) 1
Fig. 25 : THD + N vs Output Power
10 RL = 4, Vcc = 2.6V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1
Fig. 26 : THD + N vs Output Power
10 RL = 4, Vcc = 2.6V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20kHz
THD + N (%)
20kHz 0.1 20Hz, 1kHz 0.1 1E-3 0.01 Output Power (W) 0.1 1E-3 0.01 Output Power (W)
THD + N (%)
20Hz 1kHz 0.1
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TS4871
Fig. 27 : THD + N vs Output Power
10 RL = 8 Vcc = 5V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C
Fig. 28 : THD + N vs Output Power
10 RL = 8 Vcc = 5V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20Hz 20kHz
THD + N (%)
1
THD + N (%)
1
20Hz, 1kHz
20kHz
0.1
0.1 1kHz
0.01 0.1 Output Power (W) 1
1E-3
1E-3
0.01 0.1 Output Power (W)
1
Fig. 29 : THD + N vs Output Power
10 RL = 8, Vcc = 3.3V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1
Fig. 30 : THD + N vs Output Power
10 RL = 8, Vcc = 3.3V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20Hz 20kHz
THD + N (%)
20Hz, 1kHz 0.1
20kHz
THD + N (%)
0.1 1kHz
1E-3
0.01 0.1 Output Power (W)
1
1E-3
0.01 0.1 Output Power (W)
1
Fig. 31 : THD + N vs Output Power
10 RL = 8, Vcc = 2.6V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1
Fig. 32 : THD + N vs Output Power
10 RL = 8, Vcc = 2.6V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20Hz 20kHz
THD + N (%)
20Hz, 1kHz
20kHz 1kHz
0.1
1E-3
0.01 Output Power (W)
0.1
THD + N (%)
0.1
1E-3
0.01 Output Power (W)
0.1
10/28
TS4871
Fig. 33 : THD + N vs Output Power
10 RL = 8 Vcc = 5V Gv = 2 Cb = 0.1F, Cin = 1F BW < 125kHz Tamb = 25C 20kHz 20Hz 1kHz
Fig. 34 : THD + N vs Output Power
10 RL = 8, Vcc = 5V, Gv = 10 Cb = 0.1F, Cin = 1F BW < 125kHz, Tamb = 25C 20Hz
THD + N (%)
THD + N (%)
1
1 20kHz
1kHz 0.1 0.1
1E-3
0.01 0.1 Output Power (W)
1
1E-3
0.01 0.1 Output Power (W)
1
Fig. 35 : THD + N vs Output Power
10 RL = 8, Vcc = 3.3V Gv = 2 Cb = 0.1F, Cin = 1F BW < 125kHz Tamb = 25C 1 20Hz 20kHz 1kHz 0.1
Fig. 36 : THD + N vs Output Power
10 RL = 8, Vcc = 3.3V, Gv = 10 Cb = 0.1F, Cin = 1F BW < 125kHz, Tamb = 25C
THD + N (%)
THD + N (%)
1 20kHz 20Hz
1kHz 0.1
1E-3
0.01 0.1 Output Power (W)
1
1E-3
0.01 0.1 Output Power (W)
1
Fig. 37 : THD + N vs Output Power
10 RL = 8, Vcc = 2.6V Gv = 2 Cb = 0.1F, Cin = 1F BW < 125kHz Tamb = 25C 1 20Hz 20kHz 1kHz 0.1
Fig. 38 : THD + N vs Output Power
10 RL = 8, Vcc = 2.6V, Gv = 10 Cb = 0.1F, Cin = 1F BW < 125kHz, Tamb = 25C
THD + N (%)
THD + N (%)
1 20kHz 20Hz
1kHz 0.1
1E-3
0.01 Output Power (W)
0.1
1E-3
0.01 Output Power (W)
0.1
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TS4871
Fig. 39 : THD + N vs Output Power
10 RL = 16, Vcc = 5V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C
Fig. 40 : THD + N vs Output Power
10 RL = 16, Vcc = 5V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20kHz 0.1
THD + N (%)
20kHz 0.1
THD + N (%)
1
1
20Hz, 1kHz 0.01 1E-3 0.01 0.1 Output Power (W) 1
1kHz 0.01 1E-3
20Hz 1
0.01 0.1 Output Power (W)
Fig. 41 : THD + N vs Output Power
10 RL = 16, Vcc = 3.3V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20kHz 0.1
Fig. 42 : THD + N vs Output Power
10 RL = 16 Vcc = 3.3V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20kHz 0.1
THD + N (%)
THD + N (%)
1
1
1kHz 20Hz, 1kHz 0.01 1E-3 0.01 Output Power (W) 0.1 0.01 1E-3
20Hz 0.01 Output Power (W) 0.1
Fig. 43 : THD + N vs Output Power
10 RL = 16 Vcc = 2.6V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20kHz 0.1
Fig. 44 : THD + N vs Output Power
10 RL = 16 Vcc = 2.6V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20Hz 20kHz
THD + N (%)
THD + N (%)
1
1
0.1
20Hz, 1kHz 0.01 1E-3 0.01 Output Power (W) 0.1 0.01 1E-3
1kHz 0.01 Output Power (W) 0.1
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TS4871
Fig. 45 : THD + N vs Frequency Fig. 46 : THD + N vs Frequency
1
THD + N (%)
Pout = 1.2W
THD + N (%)
RL = 4, Vcc = 5V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C
Pout = 1.2W 1
0.1 RL = 4, Vcc = 5V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C 0.01 20 100 1000 Frequency (Hz)
Pout = 600mW
Pout = 600mW 0.1 20
100
1000 Frequency (Hz)
10000
10000
Fig. 47 : THD + N vs Frequency
Fig. 48 : THD + N vs Frequency
1
THD + N (%)
THD + N (%)
RL = 4, Vcc = 3.3V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C Pout = 540mW
1
RL = 4, Vcc = 3.3V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C Pout = 540mW
Pout = 270mW 0.1 20 100 1000 Frequency (Hz) 10000 0.1 20 100
Pout = 270mW 1000 Frequency (Hz) 10000
Fig. 49 : THD + N vs Frequency
Fig. 50 : THD + N vs Frequency
1
THD + N (%)
Pout = 240mW
THD + N (%)
RL = 4, Vcc = 2.6V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C
1
RL = 4, Vcc = 2.6V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C
Pout = 240 & 120mW
Pout = 120mW 0.1 20 100 1000 Frequency (Hz) 10000 0.1 20 100 1000 Frequency (Hz) 10000
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TS4871
Fig. 51 : THD + N vs Frequency
1 RL = 8 Vcc = 5V Gv = 2 Pout = 900mW BW < 125kHz Tamb = 25C
Fig. 52 : THD + N vs Frequency
1 RL = 8 Vcc = 5V Gv = 2 Pout = 450mW BW < 125kHz Tamb = 25C Cb = 0.1F
THD + N (%)
Cb = 0.1F
Cb = 1F
THD + N (%)
Cb = 1F
0.1 20 100 1000 Frequency (Hz) 10000 0.1 20 100 1000 Frequency (Hz) 10000
Fig. 53 : THD + N vs Frequency
Fig. 54 : THD + N vs Frequency
1
THD + N (%)
THD + N (%)
RL = 8, Vcc = 5V Gv = 10 Pout = 900mW BW < 125kHz Tamb = 25C Cb = 0.1F
1
RL = 8, Vcc = 5V Gv = 10 Pout = 450mW BW < 125kHz Tamb = 25C Cb = 0.1F
Cb = 1F
Cb = 1F
0.1 20 100 1000 Frequency (Hz) 10000
0.1 20 100 1000 Frequency (Hz) 10000
Fig. 55 : THD + N vs Frequency
1 RL = 8, Vcc = 3.3V Gv = 2 Pout = 400mW BW < 125kHz Tamb = 25C Cb = 0.1F
Fig. 56 : THD + N vs Frequency
1 RL = 8, Vcc = 3.3V Gv = 2 Pout = 200mW BW < 125kHz Tamb = 25C Cb = 0.1F
THD + N (%)
THD + N (%)
Cb = 1F
Cb = 1F
0.1 20 100 1000 Frequency (Hz) 10000
0.1 20 100 1000 Frequency (Hz) 10000
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TS4871
Fig. 57 : THD + N vs Frequency Fig. 58 : THD + N vs Frequency
1
THD + N (%)
Cb = 0.1F
THD + N (%)
RL = 8, Vcc = 3.3V Gv = 10 Pout = 400mW BW < 125kHz Tamb = 25C
1 Cb = 0.1F
RL = 8, Vcc = 3.3V Gv = 10 Pout = 200mW BW < 125kHz Tamb = 25C
Cb = 1F
Cb = 1F 0.1 0.1 20 100 1000 Frequency (Hz) 10000 20 100 1000 Frequency (Hz) 10000
Fig. 59 : THD + N vs Frequency
1 RL = 8, Vcc = 2.6V Gv = 2 Pout = 220mW BW < 125kHz Tamb = 25C
Fig. 60 : THD + N vs Frequency
1 RL = 8, Vcc = 2.6V Gv = 2 Pout = 110mW BW < 125kHz Tamb = 25C Cb = 0.1F
THD + N (%)
Cb = 1F
THD + N (%)
Cb = 0.1F
Cb = 1F
0.1 20 100 1000 Frequency (Hz) 10000
0.1 20 100 1000 Frequency (Hz) 10000
Fig. 61 : THD + N vs Frequency
Fig. 62 : THD + N vs Frequency
1
THD + N (%)
Cb = 0.1F
THD + N (%)
RL = 8, Vcc = 2.6V Gv = 10 Pout = 220mW BW < 125kHz Tamb = 25C
1 Cb = 0.1F
RL = 8, Vcc = 2.6V Gv = 10 Pout = 110mW BW < 125kHz Tamb = 25C
Cb = 1F
Cb = 1F 0.1 0.1 20 100 1000 Frequency (Hz) 10000 20 100 1000 Frequency (Hz) 10000
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TS4871
Fig. 63 : THD + N vs Frequency
1 RL = 16, Vcc = 5V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C
THD + N (%)
Fig. 64 : THD + N vs Frequency
1 RL = 16, Vcc = 5V Gv = 10, Cb = 1F BW < 125kHz Tamb = 25C
THD + N (%)
Pout = 620mW
Pout = 310mW 0.1
0.1
Pout = 310mW Pout = 620mW
0.01 20
100
1000 Frequency (Hz)
10000
0.01 20
100
1000 Frequency (Hz)
10000
Fig. 65 : THD + N vs Frequency
1 RL = 16, Vcc = 3.3V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C
THD + N (%)
Fig. 66 : THD + N vs Frequency
1
Pout = 270mW 0.1
THD + N (%)
RL = 16, Vcc = 3.3V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C Pout = 270mW
0.1 Pout = 135mW Pout = 135mW 0.01 20 100 1000 Frequency (Hz) 10000 20 100 1000 Frequency (Hz) 10000
Fig. 67 : THD + N vs Frequency
1 RL = 16, Vcc = 2.6V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C
THD + N (%)
Fig. 68 : THD + N vs Frequency
1 RL = 16, Vcc = 2.6V Gv = 10, Cb = 1F BW < 125kHz Tamb = 25C
THD + N (%)
Pout = 160mW
Pout = 80mW 0.1
0.1
Pout = 160mW
Pout = 80mW
0.01 20
100
1000 Frequency (Hz)
10000
0.01 20
100
1000 Frequency (Hz)
10000
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TS4871
Fig. 69 : Signal to Noise Ratio vs Power Supply with Unweighted Filter (20Hz to 20kHz)
100
Fig. 70 : Signal to Noise Ratio vs Power Supply with Weighted Filter Type A
100
90
90
RL=16
SNR (dB)
RL=8
RL=4
SNR (dB)
80
RL=8 80 RL=16 RL=4
70 Gv = 2 Cb = Cin = 1F THD+N < 0.4% Tamb = 25C 3.0 3.5
Vcc (V)
60
70
50 2.5
Gv = 10 Cb = Cin = 1F THD+N < 0.7% Tamb = 25C 3.0 3.5
Vcc (V)
4.0
4.5
5.0
60 2.5
4.0
4.5
5.0
Fig. 71 : Signal to Noise Ratio vs Power Supply with Weighted Filter type A
110
Fig. 72 : Current Consumption vs Power Supply Voltage
7 6 Vstandby = 0V Tamb = 25C
100 RL=16
SNR (dB)
RL=8
RL=4
Icc (mA)
5 4 3 2 1 0
90
80 Gv = 2 Cb = Cin = 1F THD+N < 0.4% Tamb = 25C 3.0 3.5
Vcc (V)
70
60 2.5
4.0
4.5
5.0
0
1
2
Vcc (V)
3
4
5
Fig. 73 : Signal to Noise Ratio Vs Power Supply with Unweighted Filter (20Hz to 20kHz)
90
Fig. 74 : Current Consumption vs Standby Voltage @ Vcc = 5V
7 6 Vcc = 5V Tamb = 25C
80
5
SNR (dB)
Icc (mA)
RL=8 70 RL=16 RL=4
4 3 2
60
Gv = 10 Cb = Cin = 1F THD+N < 0.7% Tamb = 25C 3.0 3.5
Vcc (V)
1 0 0.0
50 2.5
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
4.0
4.5
5.0
Vstandby (V)
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TS4871
Fig. 75 : Current Consumption vs Standby Voltage @ Vcc = 2.6V Fig. 76 : Current Consumption vs Standby Voltage @ Vcc = 3.3V
6 5 4
Icc (mA) Icc (mA)
6
Vcc = 2.6V Tamb = 25C
5 4 3 2 1 0 0.0
Vcc = 3.3V Tamb = 25C
3 2 1 0 0.0
0.5
1.0 1.5 Vstandby (V)
2.0
2.5
0.5
1.0
1.5
2.0
2.5
3.0
Vstandby (V)
Fig. 77 : Clipping Voltage vs Power Supply Voltage and Load Resistor
Fig. 78 : Clipping Voltage vs Power Supply Voltage and Load Resistor
1.0 0.9
Vout1 & Vout2 Clipping Voltage High side (V)
1.0 Tamb = 25C
Vout1 & Vout2 Clipping Voltage Low side (V)
0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 0.0 2.5
Tamb = 25C
0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 0.0 2.5 3.0 3.5 4.0 RL = 16 4.5 5.0 RL = 4 RL = 8
RL = 4 RL = 8
RL = 16 3.0 3.5 4.0 4.5 5.0
Power supply Voltage (V)
Power supply Voltage (V)
Fig. 79 : Vout1+Vout2 Unweighted Noise Floor
120
Output Noise Voltage ( V)
Fig. 80 : Vout1+Vout2 A-weighted Noise Floor
120
Output Noise Voltage ( V)
100 80 60 40 20 0 20
Vcc = 2.5V to 5V, Tamb = 25 C Cb = Cin = 1 F Input Grounded BW = 20Hz to 20kHz (Unweighted)
100 80 60 40
Av = 10
Vcc = 2.5V to 5V, Tamb = 25 C Cb = Cin = 1 F Input Grounded BW = 20Hz to 20kHz (A-Weighted)
Av = 10
Standby mode
Av = 2
Standby mode 20 0
Av = 2
100
1000 Frequency (Hz)
10000
20
100
1000 Frequency (Hz)
10000
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TS4871
APPLICATION INFORMATION Fig. 81 : Demoboard Schematic
C1 R2 C2
R1 Vcc S1 Vcc Vcc S2 GND 6 Vcc S6 C9 + 470 OUT1 S3 GND S4 GND S7 Av=-1 + Vout2 8 C10 + 470 C6 + 100 R3 Neg. input P1 R4 C4 Pos input P2 Vcc Vcc R8 D1 PW ON R7 330k 2 1 Bypass Standby Bias GND TS4871 S5 Positive Input mode R6 C5 R5 4 3 VinVin+ + C3 C7 100n
Vout1 5
S8 Standby
7 C11 + C12 1u C8
Fig. 82 : SO8 & MiniSO8 Demoboard Components Side
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TS4871
Fig. 83 : SO8 & MiniSO8 Demoboard Top Solder Layer The output power is:
Pout = (2 Vout RMS ) 2 (W ) RL
For the same power supply voltage, the output power in BTL configuration is four times higher than the output power in single ended configuration.
s Gain In Typical Application Schematic
(see page 1) In flat region (no effect of Cin), the output voltage of the first stage is: R fe ed Vout1 = - Vin ------------------- (V) Rin For the second stage : Vout2 = -Vout1 (V) Fig. 84 : SO8 & MiniSO8 Demoboard Bottom Solder
Layer
The differential output voltage is: Rfee d Vout2 - Vo ut1 = 2Vin ------------------- (V) Rin The differential gain named gain (Gv) for more convenient usage is: Vout2 - Vou t1 Rfee d Gv = -------------------------------------- = 2 ------------------Vin Rin Remark : Vout2 is in phase with Vin and Vout1 is 180 phased with Vin. It means that the positive terminal of the loudspeaker should be connected to Vout2 and the negative to Vout1.
s Low and high frequency response
In low frequency region, the effect of Cin starts. Cin with Rin forms a high pass filter with a -3dB cut off frequency. 1 FCL = ------------------------------- ( Hz ) 2 R in Cin In high frequency region, you can limit the bandwidth by adding a capacitor (Cfeed) in parallel on Rfeed. Its form a low pass filter with a -3dB cut off frequency. 1 FCH = ---------------------------------------------- ( Hz ) 2 Rfe ed Cfeed
s BTL Configuration Principle
The TS4871 is a monolithic power amplifier with a BTL output type. BTL (Bridge Tied Load) means that each end of the load is connected to two single ended output amplifiers. Thus, we have : Single ended output 1 = Vout1 = Vout (V) Single ended output 2 = Vout2 = -Vout (V) And Vout1 - Vout2 = 2Vout (V)
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TS4871 s Power dissipation and efficiency
Hypothesis : * Voltage and current in the load are sinusoidal (Vout and Iout) * Supply voltage is a pure DC source (Vcc) Regarding the load we have: VOUT = V PEAK sin t (V) and VOUT IOUT = ---------------- (A) RL and VPEAK 2 POUT = ---------------------- (W) 2 RL Then, the average current delivered by the supply voltage is: ICC
AVG
The maximum theoretical value is reached when Vpeak = Vcc, so ---- = 78.5% 4
s Decoupling of the circuit
Two capacitors are needed to bypass properly the TS4871, a power supply bypass capacitor Cs and a bias voltage bypass capacitor Cb. Cs has especially an influence on the THD+N in high frequency (above 7kHz) and indirectly on the power supply disturbances. With 100F, you can expect similar THD+N performances like shown in the datasheet. If Cs is lower than 100F, in high frequency increases, THD+N and disturbances on the power supply rail are less filtered. To the contrary, if Cs is higher than 100F, those disturbances on the power supply rail are more filtered. Cb has an influence on THD+N in lower frequency, but its function is critical on the final result of PSRR with input grounded in lower frequency. If Cb is lower than 1F, THD+N increase in lower frequency (see THD+N vs frequency curves) and the PSRR worsens up If Cb is higher than 1F, the benefit on THD+N in lower frequency is small but the benefit on PSRR is substantial (see PSRR vs. Cb curve : fig.12). Note that Cin has a non-negligible effect on PSRR in lower frequency. Lower is its value, higher is the PSRR (see fig. 13).
VPEAK = 2 ------------------- (A) RL
The power delivered by the supply voltage is Psupply = Vcc IccAVG (W) Then, the power dissipated by the amplifier is Pdiss = Psupply - Pout (W) 2 2 Vcc Pdi ss = ---------------------- POUT - POUT (W) RL and the maximum value is obtained when: Pdiss --------------------- = 0 POUT and its value is:
s Pop and Click performance
Pop and Click performance is intimately linked with the size of the input capacitor Cin and the bias voltage bypass capacitor Cb.
Pdiss max =
2 Vcc 2 2RL
(W)
Remark : This maximum value is only depending on power supply voltage and load values. The efficiency is the ratio between the output power and the power supply VPEAK POUT = ----------------------- = ---------------------Psup ply 4VCC
Size of Cin is due to the lower cut-off frequency and PSRR value requested. Size of Cb is due to THD+N and PSRR requested always in lower frequency. Moreover, Cb determines the speed that the amplifier turns ON. The slower the speed is, the softer the turn ON noise is. The charge time of Cb is directly proportional to
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TS4871
the internal generator resistance 50k. Then, the charge time constant for Cb is b = 50kxCb (s) As Cb is directly connected to the non-inverting input (pin 2 & 3) and if we want to minimize, in amplitude and duration, the output spike on Vout1 (pin 5), Cin must be charged faster than Cb. The charge time constant of Cin is in = (Rin+Rfeed)xCin (s) Thus we have the relation in << b (s) The respect of this relation permits to minimize the pop and click noise. Remark : Minimize Cin and Cb has a benefit on pop and click phenomena but also on cost and size of the application. Example : your target for the -3dB cut off frequency is 100 Hz. With Rin=Rfeed=22 k, Cin=72nF (in fact 82nF or 100nF). With Cb=1F, if you choose the one of the latest two values of Cin, the pop and click phenomena at power supply ON or standby function ON/OFF will be very small 50 kx1F >> 44kx100nF (50ms >> 4.4ms). Increasing Cin value increases the pop and click phenomena to an unpleasant sound at power supply ON and standby function ON/OFF. Why Cs is not important in pop and click consideration ? Hypothesis : * Cs = 100F * Supply voltage = 5V * Supply voltage internal resistor = 0.1 * Supply current of the amplifier Icc = 6mA At power ON of the supply, the supply capacitor is charged through the internal power supply resistor. So, to reach 5V you need about five to ten times the charging time constant of Cs (s = 0.1xCs (s)). Then, this time equal 50s to 100s << b in the majority of application. At power OFF of the supply, Cs is discharged by a constant current Icc. The discharge time from 5V to 0V of Cs is:
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5Cs tDischCs = ------------- = 83 ms Icc Now, we must consider the discharge time of Cb. At power OFF or standby ON, Cb is discharged by a 100k resistor. So the discharge time is about bDisch 3xCbx100k (s). In the majority of application, Cb=1F, then bDisch300ms >> tdischCs.
s Power amplifier design examples
Given : * * * * * * * Load impedance : 8 Output power @ 1% THD+N : 0.5W Input impedance : 10k min. Input voltage peak to peak : 1Vpp Bandwidth frequency : 20Hz to 20kHz (0, -3dB) Ambient temperature max = 50C SO8 package
First of all, we must calculate the minimum power supply voltage to obtain 0.5W into 8. With curves in fig. 15, we can read 3.5V. Thus, the power supply voltage value min. will be 3.5V. Following equation the maximum power dissipation
Pdiss max =
2 Vcc 2 2RL
(W)
with 3.5V we have Pdissmax=0.31W. Refer to power derating curves (fig. 20), with 0.31W the maximum ambient temperature will be 100C. This last value could be higher if you follow the example layout shown on the demoboard (better dissipation). The gain of the amplifier in flat region will be: VOUTPP 2 2 RL P OUT G V = -------------------- = ----------------------------------- = 5.65 VINPP VINPP We have Rin > 10k. Let's take Rin = 10k, then Rfeed = 28.25k. We could use for Rfeed = 30k in normalized value and the gain will be Gv = 6. In lower frequency we want 20 Hz (-3dB cut off frequency). Then: So, we could use for Cin a 1F capacitor value
TS4871
Application n1 : 20Hz to 20kHz bandwidth and 6dB gain BTL power amplifier. Components :
Designator R1 R4 R6 R7 R8* C5 C6 C7 C9 C10 Part Type 22k / 0.125W 22k / 0.125W Short Cicuit 330k / 0.125W (Vcc-Vf_led)/If_led 470nF 100F 100nF Short Circuit Short Circuit 1F 2mm insulated Plug 10.16mm pitch 3 pts connector 2.54mm pitch PCB Phono Jack Led 3mm TS4871ID or TS4871IS
1 CIN = ----------------------------- = 795nF 2 RinFCL which gives 16Hz. In Higher frequency we want 20kHz (-3dB cut off frequency). The Gain Bandwidth Product of the TS4871 is 2MHz typical and doesn't change when the amplifier delivers power into the load. The first amplifier has a gain of: Rfee d ----------------- = 3 R in and the theoretical value of the -3dB cut-off higher frequency is 2MHz/3 = 660kHz. We can keep this value or limit the bandwidth by adding a capacitor Cfeed, in parallel on Rfeed. Then: C FE E D 1 = -------------------------------------- = 265pF 2 R F E E DFC H
So, we could use for Cfeed a 220pF capacitor value that gives 24kHz. Now, we can calculate the value of Cb with the formula b = 50kxCb >> in = (Rin+Rfeed)xCin which permits to reduce the pop and click effects. Then Cb >> 0.8F. We can choose for Cb a normalized value of 2.2F that gives good results in THD+N and PSRR. In the following tables, you could find three another examples with values required for the demoboard. Remark : components with (*) marking are optional.
C12 S1, S2, S6, S7 S8 P1 D1* U1
Application n2 : 20Hz to 20kHz bandwidth and 20dB gain BTL power amplifier. Components :
Designator R1 R4 R6 R7 R8* C5 C6 C7 Part Type 110k / 0.125W 22k / 0.125W Short Cicuit 330k / 0.125W (Vcc-Vf_led)/If_led 470nF 100F 100nF
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TS4871
Application n4 : Differential inputs BTL power amplifier. In this configuration, we need to place these components : R1, R4, R5, R6, R7, C4, C5, C12. We have also : R4 = R5, R1 = R6, C4 = C5. The gain of the amplifier is: R1 GVDIFF = 2 ------R4 For Vcc=5V, a 20Hz to 20kHz bandwidth and 20dB gain BTL power amplifier you could follow the bill of material below. Components :
Part Type 33k / 0.125W Short Circuit 22k / 0.125W Short Cicuit 330k / 0.125W (Vcc-Vf_led)/If_led 470pF 150nF 100F 100nF Short Circuit Short Circuit 1F 2mm insulated Plug 10.16mm pitch 3 pts connector 2.54mm pitch PCB Phono Jack Led 3mm TS4871ID or TS4871IS S8 P1, P2 U1 R1 R4 R5 R6 R7 R8* C4 C5 C6 C7 C9 C10 C12 D1* Designator Part Type 110k / 0.125W 22k / 0.125W 22k / 0.125W 110k / 0.125W 330k / 0.125W (Vcc-Vf_led)/If_led 470nF 470nF 100F 100nF Short Circuit Short Circuit 1F Led 3mm
Designator C9 C10 C12 S1, S2, S6, S7 S8 P1 D1* U1
Part Type Short Circuit Short Circuit 1F 2mm insulated Plug 10.16mm pitch 3 pts connector 2.54mm pitch PCB Phono Jack Led 3mm TS4871ID or TS4871IS
Application n3 : 50Hz to 10kHz bandwidth and 10dB gain BTL power amplifier. Components :
Designator R1 R2 R4 R6 R7 R8* C2 C5 C6 C7 C9 C10 C12 S1, S2, S6, S7 S8 P1 D1* U1
S1, S2, S6, S7
2mm insulated Plug 10.16mm pitch
3 pts connector 2.54mm pitch PCB Phono Jack TS4871ID or TS4871IS
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TS4871 s Note on how to use the PSRR curves
(page 7) We have finished a design and we have chosen the components values :
Vripple
Fig. 86 : PSRR measurement schematic
Rfeed 6
* Rin=Rfeed=22k * Cin=100nF * Cb=1F Now, on fig. 13, we can see the PSRR (input grounded) vs frequency curves. At 217Hz we have a PSRR value of -36dB. In reality we want a value about -70dB. So, we need a gain of 34dB ! Now, on fig. 12 we can see the effect of Cb on the PSRR (input grounded) vs. frequency. With Cb=100F, we can reach the -70dB value. The process to obtain the final curve (Cb=100F, Cin=100nF, Rin=Rfeed=22k) is a simple transfer point by point on each frequency of the curve on fig. 13 to the curve on fig. 12. The measurement result is shown on the next figure. Fig. 85 : PSRR changes with Cb
Vcc 4 Rin Cin 3 VinVin+ +
Vcc
Vout1
5
Vs-
RL Av=-1 + Vout2 8 Vs+
2 Rg 100 Ohms 1
Bypass Standby Bias
GND
Cb
TS4871
7
s Principle of operation
* We fixed the DC voltage supply (Vcc), the AC sinusoidal ripple voltage (Vripple) and no supply capacitor Cs is used The PSRR value for each frequency is: PSRR ( d B ) = 20 x Log 10 R ms ( Vrippl e ) -------------------------------------------Rms ( Vs + - Vs - )
-30 Cin=100nF Cb=1F
-40
PSRR (dB)
Vcc = 5, 3.3 & 2.6V Rfeed = 22k, Rin = 22k Rg = 100, RL = 8 Tamb = 25C
-50 Cin=100nF Cb=100F
Remark : The measure of the Rms voltage is not a Rms selective measure but a full range (2 Hz to 125 kHz) Rms measure. It means that we measure the effective Rms signal + the noise.
-60
sHigh/low cut-off frequencies
1000 10000 100000
-70 10 100
For their calculation, please check this "Frequency Response Gain vs Cin, & Cfeed" graph:
10
Frequency (Hz)
What is the PSRR ? The PSRR is the Power Supply Rejection Ratio. It's a kind of SVR in a determined frequency range. The PSRR of a device, is the ratio between a power supply disturbance and the result on the output. We can say that the PSRR is the ability of a device to minimize the impact of power supply disturbances to the output. How do we measure the PSRR ?
Gain (dB)
5 0 -5 -10 -15 -20 -25 10 Cin = 470nF Cin = 22nF Cin = 82nF Rin = Rfeed = 22k Tamb = 25C 10000 Cfeed = 330pF Cfeed = 680pF Cfeed = 2.2nF
100 1000 Frequency (Hz)
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TS4871 PACKAGE MECHANICAL DATA
SO-8 MECHANICAL DATA
DIM. A A1 A2 B C D E e H h L k ddd 0.1 5.80 0.25 0.40 mm. MIN. 1.35 0.10 1.10 0.33 0.19 4.80 3.80 1.27 6.20 0.50 1.27 8 (max.) 0.04 0.228 0.010 0.016 TYP MAX. 1.75 0.25 1.65 0.51 0.25 5.00 4.00 MIN. 0.053 0.04 0.043 0.013 0.007 0.189 0.150 0.050 0.244 0.020 0.050 inch TYP. MAX. 0.069 0.010 0.065 0.020 0.010 0.197 0.157
0016023/C
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TS4871 PACKAGE MECHANICAL DATA
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TS4871 PACKAGE MECHANICAL DATA
Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications mentioned in this publication are subject to change without notice. This publication supersedes and replaces all information previously supplied. STMicroelectronics products are not authorized for use as critical components in life support devices or systems without express written approval of STMicroelectronics. (c) The ST logo is a registered trademark of STMicroelectronics (c) 2003 STMicroelectronics - Printed in Italy - All Rights Reserved STMicroelectronics GROUP OF COMPANIES Australia - Brazil - Canada - China - Finland - France - Germany - Hong Kong - India - Israel - Italy - Japan - Malaysia Malta - Morocco - Singapore - Spain - Sweden - Switzerland - United Kingdom - United States (c) http://www.st.com
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